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MC33215
Advance Information Telephone Line Interface and Speakerphone Circuit
The MC33215 is developed for use in fully electronic telephone sets with speakerphone functions. The circuit performs the ac and dc line termination, 2-4 wire conversion, line length AGC and DTMF transmission. The speakerphone part includes a half duplex controller with signal and noise monitoring, base microphone and loudspeaker amplifiers and an efficient supply. The circuit is designed to operate at low line currents down to 4.0 mA enabling parallel operation with a classical telephone set.
52 1
FB SUFFIX PLASTIC PACKAGE CASE 848B (TQFP-52)
* * * * * * * *
Highly Integrated Cost Effective Solution Straightforward AC and DC Parameter Adjustments Efficient Supply for Loudspeaker Amplifier and Peripherals Stabilized Supply Point for Handset Microphone Stabilized Supply Point for Base Microphone Loudspeaker Amplifier can be Powered and Used Separately Smooth Switch-Over from Handset to Speakerphone Operation Adjustable Switching Depth for Handsfree Operation ORDERING INFORMATION
Device MC33215FB MC33215B TA = -20 to +70C Operating Temperature Range Package TQFP-52 SDIP-42
42 1
B SUFFIX PLASTIC PACKAGE CASE 858 (SDIP-42)
Simplified Application
AC Impedance
DC Offset
Line Current Telephone Line
DTMF Handset Microphone Base Microphone
MF HM Attenuator Duplex Controller Rx Line Driver
Current Splitter 1:10 VCC Supply
BM
DC Slope
Receive Signal
VCC or External Supply Base Loudspeaker LS
Attenuator
Handset Earpiece
Auxiliary Input This device contains 2782 active transistors.
This document contains information on a new product. Specifications and information herein are subject to change without notice. (c) Motorola, Inc. 1997 Rev 0
MOTOROLA ANALOG IC DEVICE DATA
1
MC33215
FEATURES
Line Driver and Supply * AC and DC Termination of Telephone Line * Adjustable Set Impedance for Real and Complex Termination * Efficient Supply Point for Loudspeaker Amplifier and Peripherals * Two Stabilized Supply Points for Handset and Base Microphones * Separate Supply Arrangement for Handset and Speakerphone Operation Handset Operation * Transmit and Receive Amplifiers * Differential Microphone Inputs * Sidetone Cancellation Network * Line Length AGC * Microphone and Earpiece Mute * Separate Input for DTMF and Auxiliary Signals * Parallel Operation Down to 4.0 mA of Line Current Speakerphone Operation * Handsfree Operation via Loudspeaker and Base Microphone * Integrated Microphone and Loudspeaker Amplifiers * Differential Microphone Inputs * Loudspeaker Amplifier can be Powered and Used Separately from the Rest of the Circuit * Integrated Switches for Smooth Switch-Over from Handset to Speakerphone Operation * Signal and Background Noise Monitoring in Both Channels * Adjustable Switching Depth for Handsfree Operation * Adjustable Switch-Over and Idle Mode Timing * Dial Tone Detector in the Receive Channel
Figure 1. Pin Connections
1 2 52 N/C 51 N/C 50 VMC 49 VHF 48 VLN 47 VCC 46 N/C 45 PGD 44 LSO 43 VLS 42 LSB 41 N/C 40 N/C 3 4 LSF 39 BVO 38 PPL 37 LSI 36 VOL 35 SWD 34 TQFP-52 REF 33 AGC 32 13 VDD Gnd 31 14 TSA RLS 30 RSA 29 RSE 28 RBN 27 SWT RXO GRX PRS RXS LSM SPS N/C N/C N/C N/C N/C RXI 15 TSE 16 TBN 17 MUT 18 SPS 19 PRS 20 SWT 21 LSM (Top View) RLS 29 RSA 28 RSE 27 RBN 26 RXI 25 GRX 24 RXO 23 RXS 22 5 6 7 8 9 VCC VLN VHF VMC SLB REG SLP MFI HM1 PGD 42 LSO 41 VLS 40 LSB 39 LSF 38 BVO 37 PPL 36 LSI 35 VOL 34 SWD 33 SDIP-42 12 BM1 REF 32 AGC 31 Gnd 30
1 2 3 4 5 6 7 8 9
SLB REG SLP MFI HM1 HM2 BM2 BM1 VDD
10 HM2 11 BM2
10 TSA 11 TSE 12 TBN 13 MUT
14
15
16
17
18
19
20
21
22
23
24
25
26
(Top View)
2
MOTOROLA ANALOG IC DEVICE DATA
MC33215
MAXIMUM RATINGS
Rating Peak Voltage at VLN Maximum Loop Current Voltage at VLS (if Powered Separately) Voltage at VHF (if Externally Applied) Voltage at SPS, MUT, PRS, LSM Maximum Junction Temperature Storage Temperature Range
NOTE: ESD data available upon request.
Min -0.5 - -0.5 -0.5 -0.5 - -65
Max 12 160 12 5.5 7.5 150 150
Unit V mA V V V C C
RECOMMENDED OPERATING CONDITIONS
Characteristic Biasing Voltage at VLN Loop Current Voltage at VLS Voltage at VHF (if Externally Applied) Voltage at SPS, MUT, PRS, LSM Operating Ambient Temperature Range Min 2.4 4.0 2.4 2.4 0 -20 Max 10 130 8.0 5.0 5.0 70 Unit V mA V V V C
ELECTRICAL CHARACTERISTICS (All parameters are specified at T = 25C, Iline = 18 mA, VLS = 2.9 V, f = 1000 Hz, PRS = high, MUT = high, SPS = low, LSM = high, test figure in Figure 17 with S1 in position 1, unless otherwise stated.)
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DC LINE VOLTAGE Line Voltage Vline Parallel Operation, Iline = 4.0 mA Iline = 20 mA Iline = 70 mA V - 3.9 4.8 2.4 4.2 5.2 - 4.5 5.6 SUPPLY POINT VDD Internal Current Consumption from VDD VDD = 2.5 V DC Voltage at VMC (= VMC0) Current Available from VMC VMC = VMC0 - 200 mV - 1.2 1.5 mA SUPPLY POINT VMC 1.6 1.0 1.75 - 1.9 - V mA SUPPLY POINT VHF DC Voltage at VHF (= VHF0) 2.6 - 2.8 1.4 - 3.0 2.0 - V Internal Current Consumption from VHF VHF = VHF0 + 100 mV Current Available from VHF VHF = VHF0 - 300 mV mA mA 2.0 SUPPLY POINT VCC Current Available from VCC VCC = 2.4 V, Iline = 20 mA 13 - 15 - mA V DC Voltage Drop Between VLN and VCC Iline = 20 mA Internal Current Consumption from VLS 1.0 1.5 SUPPLY INPUT VLS - 1.0 1.5 mA
Characteristic
Min
Typ
Max
Unit
MOTOROLA ANALOG IC DEVICE DATA
3
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ELECTRICAL CHARACTERISTICS (continued) (All parameters are specified at T = 25C, Iline = 18 mA, VLS = 2.9 V, f = 1000 Hz,
PRS = high, MUT = high, SPS = low, LSM = high, test figure in Figure 17 with S1 in position 1, unless otherwise stated.)
NOTE:
Rx CHANNEL, EARPIECE AMPLIFIER
Tx CHANNEL, DTMF AMPLIFIER (MUT = LOW OR PRS = LOW)
Tx CHANNEL, BASE MICROPHONE AMPLIFIER (SPS = HIGH, Tx MODE FORCED)
Tx CHANNEL, HANDSET MICROPHONE AMPLIFIER
LOGIC INPUTS
4
Output Swing Capability into 450 THD 2%, RRXO = 360 k Output Swing Capability into 150 THD 2% Confidence Level During DTMF Dialing VMF = 7.5 mVrms, MUT = Low Psophometrically Weighted Noise Level at VEAR RXI Shorted to Gnd via 10 F Input Impedance at RXI Gain Reduction in Mute Condition MUT = Low or SPS = Low Voltage Gain from VRXI to VEAR (Note 1) Vline = 20 mVrms Gain Reduction in Mute Condition MUT = High or PRS = Low Input Impedance at MFI Voltage Gain from VMF to Vline VMF = 7.5 mVrms Gain Reduction in Mute Condition MUT = Low or PRS = Low or SPS = Low Psophometrically Weighted Noise Level at Vline BM1 and BM2 Shorted with 200 Total Harmonic Distortion at VLN VBM = 1.5 mV Common Mode Rejection Ratio Input Impedance at BM1 and BM2 Voltage Gain from VBM to Vline VBM = 0.5 mVrms Psophometrically Weighted Noise Level at Vline HM1 and HM2 Shorted with 200 Total Harmonic Distortion at VLN VHM = 4.5 mVrms Common Mode Rejection Ratio Input Impedance at HM1 and HM2 Gain Reduction in Mute Condition MUT = Low or PRS = Low or SPS = High Voltage Gain from VHM to Vline VHM = 1.5 mVrms Internal Pull Down Pin SPS Internal Pull Up Pins PRS, MUT, LSM Logic High Level Pins PRS, MUT, SPS, LSM Logic Low Level Pins PRS, MUT, SPS, LSM
1. Corresponding to -0.6 dB gain from the line to output RXO in the typical application.
Characteristic
MC33215
1800
Min
680
2.0
10
24
60
23
60
14
34
60
14
53
14
60
46
-
-
-
-
-
-
-
-
-
-
MOTOROLA ANALOG IC DEVICE DATA
55.5 Typ 130 -62 -72 100 100 15 30 24 18 35 50 18 50 18 47 - - - - - - - - - - Max 2.0 2.0 5.0 0.4 20 36 25 22 36 22 58 22 48 - - - - - - - - - - - - - mVrms Vrms mVpp mVpp dBmp dBmp Unit k k k k k k dB dB dB dB dB dB dB dB dB dB % V V %
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ELECTRICAL CHARACTERISTICS (continued) (All parameters are specified at T = 25C, Iline = 18 mA, VLS = 2.9 V, f = 1000 Hz, PRS = high, MUT = high, SPS = low, LSM = high, test figure in Figure 17 with S1 in position 1, unless otherwise stated.)
NOTE:
LOGARITHMIC AMPLIFIERS AND ENVELOPE DETECTORS
SIDETONE
BALANCE RETURN LOSS
AUTOMATIC GAIN CONTROL
Rx CHANNEL PEAK-TO-PEAK LIMITER
Rx CHANNEL, LOUDSPEAKER AMPLIFIER
Rx CHANNEL, LOUDSPEAKER PRE-AMPLIFIER (SPS = HIGH, Rx MODE FORCED)
MOTOROLA ANALOG IC DEVICE DATA
Maximum Source Current from TSE or RSE Envelope Tracking Between TSE and RSE and Between TBN and RBN Dynamic Range of Logarithmic Compression from TSA to TSE and RSA to RSE ITSA and IRSA from 2.5 A to 250 A Voltage Gain from BMI to TSA VBM = 0.5 mVrms Voltage Gain from RXI to RSA VRXI = 15 mVrms Voltage Gain from VHM to VEAR S1 in Position 2 Balance Return Loss with Respect to 600 Lowest Line Current for Minimum Gain Highest Line Current for Maximum Gain Gain Variation in Transmit and Receive Channel with Respect to Iline =18 mA with AGC Disabled (AGC to VDD) Gain Reduction in Transmit and Receive Channel with Respect to Iline = 18 mA Iline = 70 mA Peak-to-Peak Limiter Disable Threshold at PPL THD at 10 dB Overdrive VLSI = 120 mVrms Peak-to-Peak Limiter Release Time VLSI Jumps from 120 mVrms to 40 mVrms Peak-to-Peak Limiter Attack Time VLSI Jumps from 40 mVrms to 120 mVrms Gain Reduction in Mute Condition LSM = Low Output Capability into 25 THD 2%, VLS = 5.0 V, VLSI = 90 mVrms Output Capability into 25 THD 2%, VLSI = 55 mVrms Available Peak Current from LSO Confidence Level During DTMF Dialing VMF = 7.5 mVrms MUT = Low Psophometrically Weighted Noise Level at VLSP RXI Shorted to Gnd via 10 F Attenuation at Delta RVOL = 47 k Voltage Gain from VLSI to VLSP VLSI = 10 mVrms Gain Reduction in Mute Condition SPS = Low or MUT = Low Voltage Gain from VRXI to VRLS (Note 2) Vline = 20 mVrms
2. Corresponding to -0.6 dB gain from the line to output RLS in the typical application.
Characteristic
MC33215
17.5
Min
150
110
0.3
4.5
2.7
1.8
40
18
20
60
25
60
21
-
-
-
-
-
-
-
-
-
-
-
3.0
18.5
Typ
300
200
0.4
6.0
1.2
20
50
20
32
26
24
-
-
-
-
-
-
-
-
-
-
-
-
Max
19.5
250
0.5
1.5
7.5
0.1
7.0
5.0
22
28
27
27
-
-
-
-
-
-
-
-
-
-
-
-
-
mApeak
mVrms
mVrms
Unit
Vpp
Vpp
mA
mA
ms
ms
A
dB
dB
dB
dB
dB
dB
dB
dB
dB
dB
dB
dB
dB
%
V
5
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SDIP-42 Current Sunk into SWT Rx Mode 21 20 19 18 17 16 15 14 13 12 10 11 - - 9 8 7 6 5 - - 4 3 2 1 Pin TQFP-52 19 18 17 16 15 14 13 12 10 52 51 50 49 48 47 11 9 8 7 6 5 4 3 2 1 LSM SWT PRS SPS N/C N/C MUT TBN TSE TSA VDD BM1 BM2 HM2 HM1 MFI SLP REG SLB N/C N/C VMC VHF VLN VCC Name N Loudspeaker Mute Input Switch-Over Timing Adjustment Privacy Switch Input Speakerphone Select Input Not Connected Not Connected Transmit and Receive Mute Input Transmit Background Noise Envelope Timing Adjustment Transmit Signal Envelope Timing Adjustment Transmit Sensitivity Adjustment Supply Input for Speech Part Base Microphone Input 1 Base Microphone Input 2 Handset Microphone Input 2 Handset Microphone Input 1 DTMF Input DC Slope Adjustment Regulation of Line Voltage Adjustment SLP Buffered Output Not Connected Not Connected Supply Output for Handset Microphone Supply Output for Speakerphone Section and Base Microphone Line Connection Input Supply Output for Loudspeaker Amplifier and Peripherals
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ELECTRICAL CHARACTERISTICS (continued) (All parameters are specified at T = 25C, Iline = 18 mA, VLS = 2.9 V, f = 1000 Hz,
PRS = high, MUT = high, SPS = low, LSM = high, test figure in Figure 17 with S1 in position 1, unless otherwise stated.) ATTENUATOR CONTROL LOGARITHMIC AMPLIFIERS AND ENVELOPE DETECTORS Current Sourced from SWT Tx Mode Gain Variation in Idle Mode for Both Channels Adjustable Range for Switching Depth Switching Depth Speech Noise Threshold Both Channels Dial Tone Detector Threshold at Vline Maximum Source Current from TBN or RBN Maximum Sink Current into TBN and RBN Maximum Sink Current into TSE or RSE Characteristic
6 PIN FUNCTION DESCRIPTION
MC33215
Description D ii
Min
100
100
7.0
7.0
0.7
24
46
-
-
-
MOTOROLA ANALOG IC DEVICE DATA
Typ 4.5 1.0 10 10 25 50 20 - - - Max 1.3 13 13 60 54 - - - - - mVrms Unit A A A A A dB dB dB dB
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SDIP-42 42 41 40 39 38 37 36 35 34 33 32 31 30 29 28 27 26 25 24 23 22 - - - - - - Pin TQFP-52 46 45 44 43 42 41 40 39 38 37 36 35 34 33 32 31 30 29 28 27 26 25 24 23 22 21 20 N/C PGD LSO VLS LSB N/C N/C LSF BVO PPL LSI VOL SWD REF AGC Gnd RLS RSA RSE RBN N/C N/C RXI GRX RXO RXS N/C Name Not Connected Power Ground Loudspeaker Amplifier Output Supply Input for Loudspeaker Amplifier Loudspeaker Amplifier Bootstrap Output Not Connected Not Connected Loudspeaker Amplifier Feedback Input Bias Voltage for Loudspeaker Amplifier Output Peak-to-Peak Limiter Timing Adjustment Loudspeaker Amplifier Input Volume Control Adjustment Switching Depth Adjustment for Handsfree Reference Current Set Line Length AGC Adjustment Small Signal Ground Receive Output for Loudspeaker Amplifier Receive Sensitivity Adjustment Receive Signal Envelope Timing Adjustment Receive Background Noise Envelope Timing Adjustment Not Connected Not Connected Receive Amplifier Input Earpiece Amplifier Feedback Input Receive Amplifier Output Receive Amplifier Stability Not Connected
MOTOROLA ANALOG IC DEVICE DATA PIN FUNCTION DESCRIPTION (continued)
MC33215
Description
7
MC33215
DESCRIPTION OF THE CIRCUIT
Based on the typical application circuit as given in Figure 18, the MC33215 will be described in three parts: line driver and supplies, handset operation, and handsfree operation. The data used refer to typical data of the characteristics. into a small part for biasing the internal line drive transistor and into a large part for supplying the speakerphone. The ratio between these two currents is fixed to 1:10. The dc set impedance or dc setting of the telephone as created by the line driver and its external components can be approximated with the equivalent of a zener voltage plus a series resistor according to: VLN With: V zener ILN R
LINE DRIVER AND SUPPLIES
The line driver and supply part performs the ac and dc telephone line termination and provides the necessary supply points. AC Set Impedance The ac set impedance of the telephone as created by the line driver and its external components can be approximated with the equivalent circuit shown in Figure 2. Figure 2. Equivalent of the AC impedance
Inductor ZVDD 620 Zbal RREG1 360 k
+ Vzener )
REG2
ILN x R
slope
+ 0.2 x 1 ) RREG1 ) R
x 1
10 A x R
REG1
+ Iline - IVDD
+ RSLP slope 11
) RREG1 R
REG2
CVLN 10 n
CVDD 100
RSLB 2.2 k
CREG 220 n
RREG
Slope
If RREG2 is not mounted, the term between the brackets becomes equal to 1. With the values shown in the typical application and under the assumption that IVDD = 1.0 mA, the above formulas can be simplified to: VLN
Inductor
+ RREG1 x CREG x RSLP 11 + RSLP 11
x 1
Slope
) RREG1 R
REG2
+ 3.8 V ) Iline - 1.0 mA ^ 3.8 V ) Iline x 20
x 20
With the component values of the typical application, the inductor calculates as 1.6 H. Therefore, in the audio range of 300 Hz to 3400 Hz, the set impedance is mainly determined by ZVDD. As a demonstration, the impedance matching or Balance Return Loss BRL is shown in Figure 3. Figure 3. Balance Return Loss
40 35 30 25 BRL (dB) 20 15
In the typical application this leads to a line voltage of 4.2 V at 20 mA of line current with a slope of 20 . Adding a 1.5 V voltage drop for the diode bridge and the interruptor, the dc voltage at tip-ring will equal 5.7 V. If the dc mask is to be adapted to a country specific requirement, this can be done by adjusting the resistors RREG1 and RREG2, as a result, the zener voltage and the slope are varied. It is not advised to change the resistor RSLP since this changes many parameters. The influence of RREG1 and RREG2 is shown in Figure 4. Figure 4. Influence of RREG1 and RREG2 on the DC Mask
12 10 8.0 VLN (V) 6.0 4.0 2.0 0 RREG1 = 470 k RREG2 = Infinite RREG1 = 365 k RREG2 = Infinite
.
RREG1 = 470 k RREG2 = 220 k RREG1 = 365 k RREG2 = 220 k
10 5.0 0 100 1000 f, FREQUENCY (Hz) 10000
The influence of the frequency dependent parasitic components is seen for the lower frequencies (Inductor) and the higher frequencies (CVLN) by a decreasing BRL value. DC Set Impedance The line current flowing towards the MC33215 application is partly consumed by the circuitry connected to VDD while the rest flows into Pin VLN. At Pin VLN, the current is split up
0
20
40 Iline (mA)
60
80
100
As can be seen in Figure 4, for low line currents below 10 mA, the given dc mask relations are no longer valid. This is the result of an automatic decrease of the current drawn
8
MOTOROLA ANALOG IC DEVICE DATA
MC33215
from Pin REG by the internal circuit (the 10 A term in the formulas). This built-in feature drops the line voltage and therefore enables parallel operation. The voltage over the line driver has to be limited to 12 V to protect the device. A zener of 11 V at VLN is therefore the maximum advised. VDD Supply The internal circuitry for the line driver and handset interface is powered via VDD. This pin may also be used to power peripherals like a dialer or microcontroller. The voltage at VDD is not internally regulated and is a direct result of the line voltage setting and the current consumption at VDD internally (IVDD) and externally (IPER). It follows that: VLN - I I x R set DD VDD PER For correct operation, it must be ensured that VDD is biased at 1.8 V higher than SLP. This translates to a maximum allowable voltage drop across Z VDD of Vzener - 1.8 V. In the typical application, this results in a maximum allowable current consumption by the peripherals of 2.0 mA. VMC Supply At VMC, a stabilized voltage of 1.75 V is available for powering the handset microphone. Due to this stabilized supply, microphones with a low supply rejection can be used which reduces system costs. In order to support the parallel operation of the telephone set, the voltage at VMC will be maintained even at very low line currents down to 4.0 mA. Under normal supply conditions of line currents of 20 mA and above, the supply VMC is able to deliver a guaranteed minimum of 1.0 mA. However, for lower line currents, the supply capability of VMC will decrease. Figure 5. VMC Under Different Microphone Loads
1.8 1.7 1.6 1.5 VMC (V) 1.4 Iline = 4.0 mA 1.3 1.2 1.1 1.0 0 0.2 0.4 0.6 0.8 IVMC (mA) 1.0 1.2 1.4 1.6 Iline = 4.0 mA 2.7 k VMC-VHF Iline = 20 mA
If, during parallel operation, a high current is required from VMC, a 2.7 k resistor between VMC and VHF can be applied. In Figure 5, the VMC voltage under different microphone currents, is shown. VHF Supply VHF is a stabilized supply which powers the internal duplex controller part of the MC33215, and which is also meant to power the base microphone or other peripherals. The base microphone however, can also be connected to VMC, which is preferred in case of microphones with a poor supply rejection. Another possibility is to create an additional filter at VHF, like is shown in the typical application. The supply capability of VHF is guaranteed as 2.0 mA for line currents of 20 mA and greater. Since in parallel operation not enough line current is available to power a loudspeaker and thus having a speakerphone working, the current internally supplied to VHF is cut around 10 mA of line current to save current for the handset operated part. A small hysteresis is built in to avoid system oscillations. When the current to VHF is cut, the voltage at VHF will drop rapidly due to the internal consumption of 1.4 mA and the consumption of the peripherals. When VHF drops below 2.0 V, the device internally switches to the handset mode, neglecting the state of the speakerphone select Pin SPS. In case an application contains a battery pack or if it is mains supplied, speakerphone operation becomes possible under all line current conditions. In order to avoid switch-over to handset operation below the 10 mA, VHF has to be supplied by this additional power source and preferably kept above 2.4 V. VCC Supply At VCC the major part of the line current is available for powering the loudspeaker amplifier and peripheral circuitry. This supply pin should be looked at as a current source since the voltage on VCC is not stabilized and depends on the instantaneous line voltage and the current to and consumed from VCC. The maximum portion of the line current which is available at VCC is given by the following relation: 10 x I I -I -I -I line VDD VHF VCC VMC 11
V
+
)
+
This formula is valid when the voltage drop from VLN to VCC is sufficient for the current splitter to conduct all this current to VCC. When the drop is not sufficient, the current source saturates and the surplus of current is conducted to the power ground PGD to avoid distortion in the line driver. In fact, when no current is drawn from VCC, the voltage at VCC will increase until the current splitter is in balance. In Figure 6 this behavior is depicted.
MOTOROLA ANALOG IC DEVICE DATA
9
MC33215
Figure 6. Available Current at VCC
100 90 80 70 mA AND % 60 50 40 30 20 10 0 0 20 40 Iline (mA) A. Maximum Available Current at VCC 60 80 100 IVCC(max) (mA) 2.5 VLN-V CC (V) IVCC/lline (%) 2.0 1.5 1.0 0.5 0 0 20 40 Iline (mA) B. Voltage Drop to VCC 60 80 100 VCC to VLS VCC Open 3.5 3.0 IVCC at 98% of IVCC(max)
IVCC at 50% of IVCC(max)
For instance, at a line current of 20 mA a maximum of 15 mA of current is available at VCC. If all this current is taken, VCC will be 1.7 V below VLN. When not all this current is drawn from VCC, but for instance only 1.0 mA for biasing of the loudspeaker amplifier, the voltage at VCC will be 1.2 V below VLN. Although the measurements for Figure 6 are done with RREG1 = 365 k, the results are also globally valid for other dc settings. As can be seen from Figure 6, the voltage at VCC is limited by the voltage at VLN minus 1.0 V. This means that the voltage at VCC is limited by the external zener at VLN. If it is necessary to limit the voltage at VCC in order to protect peripheral circuits, a zener from VCC to Gnd can be added. If the supply of the loudspeaker VLS is also connected to VCC, it is advisable that VCC does not exceed 8.0 V. The high efficiency of the VCC power supply contributes to a high loudspeaker output power at moderate line currents. More details on this can be found in the handsfree operation paragraph.
by adjusting the sensitivity of the handset microphone by adjusting the resistors RHM1 and RHM2. It is not advised to adjust the gain by including series resistors towards the Pins HM1 and HM2. A high pass filter is introduced by the coupling capacitors CHM1 and CHM2 in combination with the input impedance. A low pass filter can be created by putting capacitors in parallel with the resistors RHM1 and RHM2. The transmit noise is measured as -72 dBmp with the handset microphone inputs loaded with a capacitively coupled 200 . In a real life application, the inputs will be loaded with a microphone powered by VMC. Although VMC is a stablized supply voltage, it will contain some noise which can be coupled to the handset microphone inputs, especially when a microphone with a poor supply rejection is used. An additional RC filter on VMC can improve the noise figure, see also the base microphone section. Handset Earpiece Amplifier The handset earpiece is to be capacitively connected to the RXO output. Here, the receive signal is available which is amplified from the line via the sidetone network and the Rx and EAR amplifiers. The sidetone network attenuates the receive signal from the line via the resistor divider composed of RSLB and Zbal, see also the sidetone section. The attenuation in the typical application by this network equals 24.6 dB. Then the signal from the sidetone network is pre-amplified by the amplifier Rx with a typical gain of 6.0 dB. This amplifier also performs the AGC and MUTE functions, see the related paragraphs. Finally, the signal is amplified by the noninverting voltage amplifier EAR. The overall receive gain ARX from the line to the earpiece output then follows as: R V RXO RXO A xA x1 A RXI RX ST R V line GRX
HANDSET OPERATION
During handset operation, the MC33215 performs the basic telephone functions for the handset microphone and earpiece. It also enables DTMF transmission. Handset Microphone Amplifier The handset microphone is to be capacitively connected to the circuit via the differential input HM1 and HM2. The microphone signal is amplified by the HMIC amplifier and modulates the line current by the injection of the signal into the line driver. This transfer from the microphone inputs to the line current is given as 15/(RSLP/11), which makes a total transmit voltage gain AHM from the handset microphone inputs to the line of: V Z x Z set line 15 A x line HM V Z Z set R 11 HM line SLP With the typical application and Zline = 600 the transmit gain calculates as 47 dB. In case an electret microphone is used, it can be supplied from the stabilized microphone supply point VMC of 1.75 V properly biased with resistors RHM1 and RHM2. This allows the setmaker to use an electret microphone with poor supply rejection to reduce total system costs. Since the transmit gain AHM is fixed by the advised RSLP = 220 and the constraints of set impedance and line impedance, the transmit gain is set
+
+
)
+
+
)
With: AST = Attenuation of the Sidetone Network ARXI = Gain of the Pre-Amplifier Rx For the typical application an overall gain from the line to the earpiece is close to 0 dB. The receive gain can be adjusted by adjusting the resistor ratio RRXO over RGRX. However, RRXO also sets the confidence tone level during dialing which leaves RGRX to be chosen freely. A high pass filter is introduced by the coupling capacitor CRXI together with the input impedance of the input
10
MOTOROLA ANALOG IC DEVICE DATA
MC33215
RXI. A second high pass filtering is introduced by the combination of CGRX and RGRX. A low pass filter is created by CRXO and RRXO. The coupling capacitor at the output RXO is not used for setting a high pass filter but merely for dc decoupling. In combination with dynamic ear capsules, the EAR amplifier can become unstable due to the highly inductive characteristic of some of the capsules. To regain stability, a 100 nF capacitor can be connected from RXS to Gnd in those cases. An additional 10 nF at the RXI input, as shown in the typical application, improves the noise figure of the receiver stage. Sidetone Cancellation The line driver and the receiver amplifier of the MC33215 are tied up in a bridge configuration as depicted in Figure 7. This bridge configuration performs the so-called hybrid function which, in the ideal case, prevents transmitted signals from entering the receive channel. Figure 7. Sidetone Bridge
VLN
Automatic Gain Control To obtain more or less constant signal levels for transmit and receive regardless of the telephone line length, both the transmit and receive gain can be varied as a function of line current when the AGC feature is used. The gain reduction as a function of line current, and thus line length, is depicted in Figure 8. Figure 8. Automatic Gain Control
0 -1.0 -2.0 AGC (dB) RAGC = 30 k -3.0 -4.0 -5.0 -6.0
RAGC = 20 k
0
10
20
30
40
50
60
70
Iline (mA) Zbal RXI Receive RSLB Gnd
Zline//Zset Gnd RSLP/11 Transmit
V
HM R 11 SLP
x 15
SLP
As can be seen from Figure 7 by inspection, the receiver will not pick up any transmit signal when the bridge is in balance, that is to say when: Z Z Z set bal line R R 11 SLB SLP The sidetone suppression is normally measured in an acoustic way. The signal at the earpiece when applying a signal on the microphone is compared with the signal at the earpiece when applying a signal on the line. The suppression takes into account the transmit and receive gains set. In fact the sidetone suppression can be given as a purely electrical parameter given by the properties of the sidetone bridge itself. For the MC33215, this so-called electrical sidetone suppression ASTE can be given as: R 11 Z SLP A 1 - bal x STE R Z Z set SLB line Values of -12 dB or better, thus ASTE < 0.25, can easily be reached in this way.
For small line currents, and thus long lines, no gain reduction is applied and thus the transmit and receive gains are at their maximum. For line currents higher than Istart, the gain is gradually reduced until a line current Istop is reached. This should be the equivalent of a very short line, and the gain reduction equals 6.0 dB. For higher line currents the gain is not reduced further. For the start and stop currents the following relations are valid: 1 I stop R 11 SLP
+
+
AGC 11 R 11 SLP SLP For the typical application, where RAGC = 30 k, the gain will start to be reduced at Istart = 20 mA while reaching 6.0 dB of gain reduction at Istop = 50 mA. When AGC is connected to VDD, the AGC function is disabled leading to no gain reduction for any line current. This is also sometimes called PABX mode. The automatic gain control takes effect in the HMIC and Rx amplifiers as well as in the BMIC amplifier. In this way the AGC is also active in speakerphone mode, see the handsfree operation paragraph. I start 1 - Privacy and DTMF Mode During handset operation a privacy and a DTMF mode can be entered according the logic Table 1.
+R
20 x R
+
Table 1. Logic Table for Handset Mode
Logic Inputs SPS 0 0 0 MUT 1 1 0 PRS 1 0 Mode Md HMIC On Off Off BMIC Off Off Off Amplifiers DTMF Off Rx RXatt Off Off Off EAR On On On
AAA A A AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AA AA A A AA AAA A A A A A A AA AA A A AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AA AA A AA AA A A AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AA AA A A AA
Handset Normal On On Off Handset Privacy Handset DTMF On On X
MOTOROLA ANALOG IC DEVICE DATA
11
MC33215
Table 2. Logic Table for Handsfree Mode
Logic Inputs SPS 1 1 1 MUT 1 1 0 PRS 1 0 Mode Md HMIC Off Off Off BMIC On Off Off Amplifiers DTMF Off Rx RXatt On On On EAR Off Off Off
AAA A A AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AA AA A A AA AAA A A A A A AA A AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAA A A A A A AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AA AA A AA AA A A AA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAA A AA A A AA
Handsfree Normal On On Off Handsfree Privacy Handsfree DTMF On On X
By applying a logic 0 to Pin MUT, the DTMF mode is entered where the DTMF amplifier is enabled and where the Rx amplifier is muted. A DTMF signal can be sent to the line via the MFI input for which the gain ADTMF is given as: V Z x Z set line 3.75 A x line DTMF V Z Z set R 11 MFI line SLP In the typical application, the gain equals 35 dB. The DTMF gain can be controlled by a resistor divider at the input MFI as shown in the typical application. The signal has to be capacitively coupled to the input via CMFI which creates a high pass filter with the input impedance. The line length AGC has no effect on the DTMF gains. The signal applied to the MFI input is made audible at the earpiece output for confidence tone. The signal is internally applied to the GRX pin where it is amplified via the EAR amplifier which is used as a current to voltage amplifier. The gain is therefore proportional to the feedback resistor RRXO. For RRXO = 180 k the gain equals 6.0 dB. The confidence tone is also audible at the loudspeaker output when the loudspeaker amplifier is activated, see speakerphone operation. By applying a logic 0 to Pin PRS, the MC33215 enters privacy mode. In this mode, both handset and handsfree microphone amplifiers are muted while the DTMF amplifier is enabled. Through the MFI input, a signal, for example music on hold, can be sent to the line. In the same way, the MFI input can also be used to couple in signals from, for instance, an answering machine.
+
+
)
With the typical application and Zline = 600 the transmit gain calculates as 55 dB. The electret base microphone can be supplied directly from VHF but it is advised to use an additional RC filter to obtain a stable supply point, as shown in the typical application. The microphone can also be supplied by VMC. The transmit gain is set by adjusting the sensitivity of the base microphone by adjusting the resistors RBM1 and RBM2. It is not advised to adjust the gain by including series resistors towards the Pins BM1 and BM2. A high pass filter is introduced by the coupling capacitors CBM1 and CBM2 in combination with the input impedance. A low pass filter can be created by putting capacitors in parallel with the resistors RBM1 and RBM2.
HANDSFREE OPERATION
Handsfree operation, including DTMF and Privacy modes, can be performed by making Pin SPS high according Table 2. The handset amplifiers will be switched off while the base amplifiers will be activated. The MC33215 performs all the necessary functions, such as signal monitoring and switch-over, under supervision of the duplex controller. With the MC33215 also a group listening-in application can be built. For more information on this subject please refer to application note AN1574. Base Microphone Amplifier The base microphone can be capacitively connected to the circuit via the differential input BM1 and BM2. The setup is identical to the one for the handset microphone amplifier. The total transmit voltage gain ABM from the base microphone inputs to the line is: V Z x Z set line 37.5 A x line BM V Z Z set R 11 BM line SLP
Loudspeaker Amplifier The loudspeaker amplifier of the MC33215 has three major benefits over most of the existing speakerphone loudspeaker amplifiers: it can be supplied and used in a telephone line powered application but also stand alone, it has an all NPN bootstrap output stage which provides maximum output swing under any supply condition, and it includes a peak-to-peak limiter to limit the distortion at the output. The loudspeaker amplifier is powered at Pin VLS. In telephone line powered applications, this pin should be connected to VCC where most of the line current is available, see the VCC supply paragraph. In an application where an external power supply is used, VLS and thus the loudspeaker amplifier can be powered separately from the rest of the circuit. The amplifier is grounded to PGD, which is the circuits power ground shared by both the loudspeaker amplifier and the current splitter of the VCC supply. Half the supply voltage of VLS is at BVO, filtered with a capacitor to VLS. This voltage is used as the reference for the output amplifier. The receive signal present at RLS can be capacitively coupled to LSI via the resistor RLSI. The overall gain from RLS to LSO follows as: V R LSO A - LSF x 4.0 LS V R RLS LSI In the typical application this leads to a loudspeaker gain ALS of 26 dB. The above formula follows from the fact that the overall amplifier architecture from RLS to LSO can be looked at as an inverting voltage amplifier with an internal current gain from LSI to LSF of 4. The input LSI is a signal current summing node which allows other signals to be applied here.
+
+
+
+
)
12
MOTOROLA ANALOG IC DEVICE DATA
MC33215
Figure 9. Loudspeaker Output Stage
0.5 VLS 0 -0.5 VLS Loudspeaker 1.5 VLS VLS VLS 0.5 VLS
LSB VLS CLSO T2
LSO T1 VLS 0.5 VLS 0 PGD
Figure 10. Loudspeaker Amplifier Output Power with External Supply
140 120 100 P LSP (mW) 80 60 40 20 0 2.0 3.0 4.0 5.0 VLS (V) A. Peak-to-Peak Limiter Active 6.0 7.0 8.0 RLSP = 50 50 0 2.0 P LSP (mW) RLSP = 25 300 250 200 150 100 RLSP = 50 RLSP = 25
3.0
4.0
5.0 VLS (V)
6.0
7.0
8.0
B. Peak-to-Peak Limiter Disabled
The total gain from the telephone line to the loudspeaker output includes, besides the loudspeaker amplifier gain, also the attenuation of the sidetone network and the internal gain from RXI to RLS. When in receive mode, see under duplex controller, the gain from RXI to RLS is maximum and equals 24 dB at maximum volume setting. The attenuation of the sidetone network in the typical application equals 24.6 dB which makes an overall gain from line to loudspeaker of 25.4 dB. Due to the influence of the line length AGC on the Rx amplifier, the gain will be reduced for higher line currents. The output stage of the MC33215 is a modified all NPN bootstrap stage which ensures maximum output swing under all supply conditions. The major advantage of this type of output stage over a standard rail-to-rail output is the higher stability. The principle of the bootstrap output stage is explained with the aid of Figure 9. The output LSO is biased at half the supply VLS while the filtering of the loudspeaker with the big capacitor CLSO requires that LSB is biased at VLS. In fact, because of the filtering, LSB is kept at VLS/2 above the LSO output even if LSO contains an ac signal. This allows the output transistor MOTOROLA ANALOG IC DEVICE DATA
T2 to be supplied for output signals with positive excursions up to VLS without distorting the output signal. The resulting ac signal over the loudspeaker will equal the signal at LSO. As an indication of the high performance of this type of amplifier, in Figure 10, the output power of the loudspeaker amplifier as a function of supply voltage is depicted for 25 and 50 loads with both the peak-to-peak limiter active and disabled. As can be seen, in case the peak-to-peak limiter is disabled, the output power is roughly increased with 6.0 dB, this at the cost of increased distortion levels up to 30%. In a telephone line powered application, the loudspeaker amplifier output power is limited not only by the supply voltage but also by the telephone line current. This means that in telephones the use of 25 or 50 speakers is preferred over the use of the cheaper 8.0 types. Figure 11 gives the output power into the loudspeaker for a line powered application and two different dc settings with the peak-to-peak limiter active. In case the peak-to-peak limiter is disabled the output power will be increased for the higher line currents up to 6.0 dB.
13
MC33215
100 90 80 70 RREG1 = 365 k RREG2 = Infinite 50 RLSP = 25 RREG1 = 365 k 40 RREG2 = Infinite 30 R = 50 LSP 20 60 10 0 dA LSP (dB) 0 20 40 Iline (mA) 60 80 100 PLSP (mW) RREG1 = 365 k RREG2 = 220 k RLSP = 50
Figure 11. Loudspeaker Amplifier Output Power when Line Powered
RREG1 = 365 k RREG2 = 220 k RLSP = 25
loudspeaker amplifier is muted which is needed for correct handset operation. The volume of the loudspeaker signal can be varied via a potentiometer at VOL. A fixed current of 10 A is running through the potentiometer and the resulting voltage at VOL is a measure for the gain reduction. The relation between the voltage at VOL and the obtained gain reduction is given in Figure 13. Figure 13. Volume Reduction
0 -5.0 -10 -15 -20 -25 -30 -35 -40 0 100 200 300 400 500 VVOL (mV), dALSP (dB)
The quality of the audio output of the loudspeaker amplifier is mainly determined by the distortion level. To keep high quality under difficult supply conditions, the MC33215 incorporates a peak-to-peak limiter. The peak-to-peak limiter will detect when the output stage gets close to its maximum output swing and will then reduce the gain from LSI to LSF. The attack and release of the limiter is regulated by the CPPL capacitor. Figure 12 depicts the limiter's attack behavior with CPPL = 100 nF. The release time is given as 3 x CPPL x RPPL. In the typical application this leads to a release time of 300 ms. Figure 12. Peak-to-Peak Limiter Dynamic Behavior
It can be seen from Figure 13 that a linear variation of RVOL will give a logarithmic gain reduction which adapts better to the human ear than a linear gain reduction. During DTMF dialing, see Table 2, a confidence tone is audible at the loudspeaker of which the level is proportional to the feedback resistor RLSF only. At RLSF = 180 k the gain from MFI to LSO equals 28.5 dB. Half Duplex Controller To avoid howling during speakerphone operation, a half duplex controller is incorporated. By monitoring the signals in both the transmit and receive channel the duplex controller will reduce the gain in the channel containing the smallest signal. A typical gain reduction will be between 40 dB and 52 dB depending on the setting, see below. In case of equal signal levels or by detection of noise only, the circuit goes into idle mode. In this mode the gain reduction in both channels is halfway, leading to 20 dB to 26 dB of reduction. In a speakerphone built around the MC33215, following the signal path from base microphone to the line and via sidetone, loudspeaker and acoustic coupling back to the microphone, the loop gain can be expressed as a sum of the gains of the different stages. However, since the transmit and receive gains are dependent on AGC and the sidetone suppression is dependent on matching with the different lines we are mostly interested by the maximum possible loop gain ALOOP(max). It follows: ALOOP(max) = ABMRX(max) + ARXBM(max) - ASWD (dB) With: ABMRX(max) = Maximum gain from BM1 and BM2 to RXI as a function of line length AGC and line impedance matching ARXBM(max) = Maximum gain from RXI to BM1 and BM2 as a function of line length AGC and acoustic coupling
VLSO 0.5 V/DIV
VPPL Vin 0 1.0 2.0 3.0 t, TIME (ms) 4.0 5.0 6.0
Figure 12 clearly shows that due to the action of the peak-to-peak limiter, the output swing and thus the output power is reduced with respect to the maximum possible as already indicated in Figure 10. The peak-to-peak limiter can be disabled by connecting the PPL pin to ground. On top of the peak-to-peak limiter, the MC33215 incorporates a supply limiter, which reduces the gain rapidly when the supply voltage VLS drops too much. This will avoid malfunctioning of the amplifier and unwanted oscillations. The voltage drop is detected via the BVO input and for that reason the CBVO has to be connected to VLS and not to Gnd. The amplifier can be activated by making Pin LSM high. In the typical application this pin is connected to SPS, which activates the loudspeaker amplifier automatically when the speakerphone mode is entered. When LSM is made low, the
14
MOTOROLA ANALOG IC DEVICE DATA
MC33215
A SWD = Switching depth as performed in the attenuators To avoid howling, the maximum possible loop gain should be below 0 dB and preferably below -10 dB for comfort. In a practical telephone design, both the ABMRX(max) and the ARXBM(max) will be less than 20 dB thus a switching depth of 50 dB will give a loop gain of less than -10 dB. An optimized sidetone network is of high importance for handsfree operation. The better the network matches with the telephone line the less local feedback and the smaller the switching range can be. The amount of gain reduction ASWD obtained by the duplex controller is set via resistor RSWD according: 2 3.6 x R SWD (dB) A 20 log SWD R REF mode, due to the coupling of the high loudspeaker signal, is automatically taken into account. In the table, two particulars can be found. At first, the set will go to idle mode if the signals are not at least 4.5 dB greater then the noise floor, which calculates as a 13 mV voltage difference in envelopes. This avoids continuous switching over between the modes under slight variations of the background noise due to, for instance, typing on a keyboard. Second, a dial tone detector threshold is implemented to avoid that the set goes to idle mode in presence of a continuous strong receive signal like a dial tone. The dial tone detector threshold is proportional to the RRSA resistor. In the typical application with RRSA = 3.3 k, the threshold is at 1.26 mVrms at the input RXI or 20 mVrms at the line. Line length AGC is of influence on the dial tone detector threshold, increasing the level depending on the line current with a maximum of 6.0 dB. In order to perform a correct comparison between the signal strengths, the sensitivity of the envelope detectors can be adjusted via the resistors connected to TSA and RSA. Based on the above, and on the fact that there is an effective gain of 20 dB in the transmit monitor, it can be derived that for stable operation the following two relations are valid: 20 log R
+
In the typical application the gain reduction will be 50 dB. To compare the transmit and receive signals with each other, they have to be monitored. This is done by making a signal envelope and a background noise envelope via the CTSE, CTBN capacitors for the transmit channel and via the CRSE, CRBN capacitors for the receive channel. In Figure 14, a schematic behavior of the envelopes is depicted which is equal for both transmit and receive. The voltage signal at the input is first transferred to a current via the sensitivity adjust network. Then this current is led through a diode which gives a logarithmic compression in voltage. It is this voltage from which the signal envelope is created by means of asymmetric charge and discharge of the signal envelope capacitor. The noise envelope voltage then follows in a similar way. Based on the envelope levels, the MC33215 will switch to transmit, receive or idle mode following Table 3. The fact that in receive mode the signal on the base microphone is greater than it is in case of transmit
t 20 log RRSA - ABMRX(max) ) 20 (dB) 20 log R u 20 log RRSA - ARXBM(max) TSA -A ) 20 (dB) SW
TSA
By measuring the gains and choosing the RRSA, the limits for RTSA follow. The choice for the sensitivity resistors is not completely free. The logarithmic compressors and the amplifier stages have a certain range of operation and, on the receive side, the choice for RRSA is given by the desired dial tone detector threshold. Figure 15 indicates the available dynamic range for the selected value of the sensitivity resistors.
Figure 14. Signal and Noise Envelopes
1.8 V Internal VHF CTSE TSE Microphone Input Signal TSA RTSA CTSA VHF CTBN TBN
MOTOROLA ANALOG IC DEVICE DATA
15
MC33215
Table 3. Logic Table for Switch-Over
VBM1 (Vrms)
VRXI (Vrms)
AAAAAAA A A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A A A AAAAAAA A A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAA A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAA A A A AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA A A A A
1 1 0 0 0 1 0 X X 1 0 0 X X X 1 0 Transmit Idle X X X Receive Receive Idle
TSE > RSE
TSE > TBN + 13 mV
RSE > VDDT
RSE > RBN + 13 mV
Mode
The resistors for the sensitivity setting have to be coupled capacitively to the pins for dc decoupling, and also to create a high pass filter to suppress low frequent background noises like footsteps and 50 Hz. The switch-over timing is performed by charging and discharging the CSWT capacitor. The switch-over from transmit to receive or vice versa is fast, on the order of milliseconds, and is proportional to the value of CSWT. The switch-over to idle mode is slow, in the order of a few seconds, and is proportional to the product of the values of RSWT and CSWT. Figure 16 depicts a typical switch-over behavior when applying transmit and receive stimuli.
The electrical characteristics and the behavior of the MC33215 are not the only factor in designing a handsfree speakerphone. During the design the acoustics have to be taken into account from the beginning. The choice of the transducers and the design of the cabinet are of great influence on the speakerphone performance. Also, to achieve a proper handsfree operation, the fine tuning of the components around the duplex controller have to be done with the final choice of the cabinet and the transducers.
Figure 15. Compression Range of the Signal Monitors
100.0E-3 Upper Limit of Compression 10.0E-3 Dial Tone Threshold Lower Limit of Compression 10.0E-3 Lower Limit of Compression 1.0E-3 100.0E-3 Upper Limit of Compression
1.0E-3
100.0E-6
10.0E-6 100
1000 RRSA ()
10000
100000
100.0E-6 100
1000 RTSA ()
10000
100000
A. Receive Monitor
B. Transmit Monitor
Figure 16. Switch-Over Behavior
Receive
Transmit
VMC + 0.5 SWT VMC - 0.5
16
MOTOROLA ANALOG IC DEVICE DATA
MC33215
Figure 17. Test Circuit
ZVDD 620 VDD Gnd CVDD 100 VDD RREG 360 k CREG 220 n REG VLN VMC Supply 1:10 VHF VCC CHM1 33 n HM1 VHM HM2 CHM2 33 n CBM1 33 n BM1 VBM CBM2 33 n BM2 CTSA 470 n RTSA 2.2 k TSA TSE VHF CTSE 330 n TBN CTBN 4.7 RAGC 30 k AGC RREF 20 k REF RSWD 100 k SWD VOL RVOL 47 k RLS V VRLS CBVO 220 n VLS V VLSP CLSO 47 RLSO
180 k
Zbal 33 k RSLB 2.2 k CVMC 10 CVHF 47 CVCC 470 RSLP 220
Vline V
600 Vac Iline
Supply
MC33215
MHM Driver HMIC 0.2 V AGC MBM BMIC AGC MHM Tx Log-Amp and Envelope Detectors MBM MDF MRX MRA Attenuator Control AGC Analog Control Block Rx Log-Amp and Envelope Detectors MEAR SWT Logic Control Block PRS Tx Attenuator MDF MFI DTMF SPS 1x SLB
SLP
CMF1 47 n VMF VSPS
MUT VMUT VPRS LSM VLSM CRBN RBN 4.7 CRSE RSE 330 n RSA MRX RRSA 3.3 k Rx AGC MEAR CEAR 10 RRXO 180 k RGRX 24 k CGRX 47 n V VEAR RXI CRXI 47 n 2 S1 1 VRXI VSWT VHF CRSA 470 n
Rx Attenuator
BVO VLS 25 LSB LSO PGD LSP Peak Limiter EAR MRA
RXO
GRX
LSF PPL RPPL
1.0 M
LSI CPPL 100 n RLSI 36 k CLSI 47 n
RXS CRXS 100 n
VLSI
MOTOROLA ANALOG IC DEVICE DATA
17
MC33215
Figure 18. Typical Application
T1 ZVDD 620 VDD Gnd CVDD 100 VDD RREG1 365 k RREG2 CREG 220 n REG VLN VMC Zbal 33 k Z1 10 V 0.01
Hook Switch
RSLB 2.2 k T2 CVMC 10 CVHF 47 CVCC 470 VDD
Supply VMC RHM1 1.0 k CHM1 33 n HM1 CHM2 33 n HM2 VHF 1.0 k 10 F RBM2 1.0 k RBM1 1.0 k RHM2 1.0 k CBM1 33 n BM1 CBM2 33 n BM2 BMIC HMIC
MC33215
Supply 1:10
VHF VCC
MHM Driver 1x 0.2 V AGC MBM MDF Tx Attenuator MFI DTMF SLB
SLP
RSLP 220 Tip CMF1 47 n Ring Dialer or Microcontroller 1 4 7 Privacy Button * Speakerphone Button 2 5 8 0 3 6 9 #
AGC RTSA 470 TSA MHM TSE CTSE 330 n CTBN 4.7 RAGC 30 k RREF 20 k RSWD 100 k AGC REF Analog Control Block Attenuator Control Tx Log-Amp and Envelope Detectors MBM MDF MRX MRA MEAR Logic Control Block
SPS MUT
CTSA 1.0 F VHF
PRS LSM
TBN
CSWT SWT 100 n
VMC
AGC Rx Log-Amp and Envelope Detectors
RBN
CRBN 4.7 CRSE 330 n
RSWT 2.2 M
SWD VOL
RSE RSA
VHF CRSA 470 n
RVOL 50 k RLS BVO VCC CBVO 220 n MRA VLS Rx Attenuator
MRX Rx RXI
RRSA 3.3 k
CRXI 33 n AGC MEAR
10 n
LSB 25 CLSO 47 RLSO 180 k RXO LSO PGD LSP Peak Limiter GRX RGRX 24 k CGRX 47 n EAR RRXO 180 k
CEAR 10 150
LSF PPL RPPL 1.0 M CPPL 100 n LSI RXS CRXS 100 n
CRLS 33 n
RLSI 36 k
18
MOTOROLA ANALOG IC DEVICE DATA
MC33215
OUTLINE DIMENSIONS
FB SUFFIX PLASTIC PACKAGE CASE 848B-04 (TQFP-52) ISSUE C
L
B B
39 40
27 26 S S
D
D
-A-, -B-, -D- DETAIL A
DETAIL A -A- L -B- B
S
H A-B
0.05 (0.002) A-B
V
C A-B
S
F
M
0.20 (0.008)
0.20 (0.008)
M
J
N
52 1 13
14
BASE METAL
-D- B 0.20 (0.008) M H A-B 0.05 (0.002) A-B V 0.20 (0.008)
M
D 0.02 (0.008)
M
C A-B
S
D
S
S
D
S
SECTION B-B
NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DATUM PLANE -H- IS LOCATED AT BOTTOM OF LEAD AND IS COINCIDENT WITH THE LEAD WHERE THE LEAD EXITS THE PLASTIC BODY AT THE BOTTOM OF THE PARTING LINE. 4. DATUMS -A-, -B- AND -D- TO BE DETERMINED AT DATUM PLANE -H-. 5. DIMENSIONS S AND V TO BE DETERMINED AT SEATING PLANE -C-. 6. DIMENSIONS A AND B DO NOT INCLUDE MOLD PROTRUSION. ALLOWABLE PROTRUSION IS 0.25 (0.010) PER SIDE. DIMENSIONS A AND B DO INCLUDE MOLD MISMATCH AND ARE DETERMINED AT DATUM PLANE -H-. 7. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.08 (0.003) TOTAL IN EXCESS OF THE D DIMENSION AT MAXIMUM MATERIAL CONDITION. DAMBAR CANNOT BE LOCATED ON THE LOWER RADIUS OR THE FOOT. MILLIMETERS MIN MAX 9.90 10.10 9.90 10.10 2.10 2.45 0.22 0.38 2.00 2.10 0.22 0.33 0.65 BSC --- 0.25 0.13 0.23 0.65 0.95 7.80 REF 5_ 10_ 0.13 0.17 0_ 7_ 0.13 0.30 12.95 13.45 0.13 --- 0_ --- 12.95 13.45 0.35 0.45 1.6 REF INCHES MIN MAX 0.390 0.398 0.390 0.398 0.083 0.096 0.009 0.015 0.079 0.083 0.009 0.013 0.026 BSC --- 0.010 0.005 0.009 0.026 0.037 0.307 REF 5_ 10_ 0.005 0.007 0_ 7_ 0.005 0.012 0.510 0.530 0.005 --- 0_ --- 0.510 0.530 0.014 0.018 0.063 REF
C A-B
S
D
S
C E
M_
DETAIL C
-H-
DATUM PLANE
0.10 (0.004) H G M_ -C-
SEATING PLANE
U_
R Q_ T W X DETAIL C K
DIM A B C D E F G H J K L M N Q R S T U V W X
MOTOROLA ANALOG IC DEVICE DATA
19
MC33215
OUTLINE DIMENSIONS
B SUFFIX PLASTIC PACKAGE CASE 858-01 (SDIP-42) ISSUE O
-A-
42 22
-B-
1 21
NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: INCH. 3. DIMENSION L TO CENTER OF LEAD WHEN FORMED PARALLEL. 4. DIMENSIONS A AND B DO NOT INCLUDE MOLD FLASH. MAXIMUM MOLD FLASH 0.25 (0.010). INCHES MIN MAX 1.435 1.465 0.540 0.560 0.155 0.200 0.014 0.022 0.032 0.046 0.070 BSC 0.300 BSC 0.008 0.015 0.115 0.135 0.600 BSC 0_ 15 _ 0.020 0.040 MILLIMETERS MIN MAX 36.45 37.21 13.72 14.22 3.94 5.08 0.36 0.56 0.81 1.17 1.778 BSC 7.62 BSC 0.20 0.38 2.92 3.43 15.24 BSC 0_ 15_ 0.51 1.02
L C H
-T-
SEATING PLANE
F D 42 PL 0.25 (0.010)
M
G TA
S
N K J 42 PL 0.25 (0.010)
M
M TB
S
DIM A B C D F G H J K L M N
Motorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation consequential or incidental damages. "Typical" parameters which may be provided in Motorola data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including "Typicals" must be validated for each customer application by customer's technical experts. Motorola does not convey any license under its patent rights nor the rights of others. Motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the Motorola product could create a situation where personal injury or death may occur. Should Buyer purchase or use Motorola products for any such unintended or unauthorized application, Buyer shall indemnify and hold Motorola and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that Motorola was negligent regarding the design or manufacture of the part. Motorola and are registered trademarks of Motorola, Inc. Motorola, Inc. is an Equal Opportunity/Affirmative Action Employer. Mfax is a trademark of Motorola, Inc. How to reach us: USA / EUROPE / Locations Not Listed: Motorola Literature Distribution; P.O. Box 5405, Denver, Colorado 80217. 303-675-2140 or 1-800-441-2447 JAPAN: Nippon Motorola Ltd.; Tatsumi-SPD-JLDC, 6F Seibu-Butsuryu-Center, 3-14-2 Tatsumi Koto-Ku, Tokyo 135, Japan. 81-3-3521-8315
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20
MC33215/D MOTOROLA ANALOG IC DEVICE DATA

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